The work deals with design of novel pipelined AD converter using switched-capacitors approach.

The work deals with the design of novel high order sigma-delta AD converter using switched-capacitors approach. Model of the ideal and real architecture of the third order sigma-delta modulator was designed in MATLAB SIMULINK. The comparison of the ideal and real model of sigma delta architecture is described in this thesis. On the basis of simulation results in MATLAB SIMULINK the stages of modulator on transistors level in CMOS technology were designed. Fully differential operational amplifier, switched capacitor integrator, summing amplifier, comparator, one bit digital to analog converter and nonoverlapping clock generator were designed. The circuit of third order sigma-delta modulator was simulated in CADENCE. Layout of operational amplifier and switched capacitor integrator was made. Through the use of MATLAB was designed decimation filter as well.

This thesis explores high voltage converter circuits for MEMS applications using micromachined devices. A novel MEMS based tunable DC-DC converter has been developed. Conventional high voltage converters based on charge pumps are unable to convert voltages to higher than few tens of volts due to power handling limitations of the CMOS components. In order to overcome this limitation a high voltage circuit has been proposed, which when integrated with micromachined switches will generate output voltages in the range of 100 Volts. The converter is based on a two phase switched capacitor circuit, and allows regulation of voltage conversion ratio. Three prototype circuits have been built for proof of concept. A test program has been written for synchronized CPLD based control of the switched capacitors. Individual capacitor fabrication technology is explored using two methods - Porous Silicon and DRIE processing. A micromachined capacitor bank has also been fabricated in silicon using a novel process sequence which provides for critical real estate savings and integration benefits. It enables on-chip integration of numerous microcapacitors, without losing customized configurability of the capacitor bank. The technique utilizes polyimide to facilitate lithography on a highly contoured surface. Plain capacitors have been fabricated on silicon with oxide-nitride-oxide stack being used as the dielectric to provide a building block for further fabrication of a variety of capacitors.

abstract: Semiconductor device scaling has kept up with Moore's law for the past decades and they have been scaling by a factor of half every one and half years. Every new generation of device technology opens up new opportunities and challenges and especially so for analog design. High speed and low gain is characteristic of these processes and hence a tradeoff that can enable to get back gain by trading speed is crucial. This thesis proposes a solution that increases the speed of sampling of a circuit by a factor of three while reducing the specifications on analog blocks and keeping the power nearly constant. The techniques are based on the switched capacitor technique called Correlated Level Shifting. A triple channel Cyclic ADC has been implemented, with each channel working at a sampling frequency of 3.33MS/s and a resolution of 14 bits. The specifications are compared with that based on a traditional architecture to show the superiority of the proposed technique. / Dissertation/Thesis / Ph.D. Electrical Engineering 2012

Power distribution network (PDN) design was a non-existent entity during the early days of microprocessors due to the low frequency of operation. Once the switching frequencies of the microprocessors started moving towards and beyond MHz regions, the parasitic inductance of the PCB tracks and planes started playing an important role in determining the maximum voltage on a PDN. Voltage regulator module (VRM) sup-plies only the DC power for microprocessors. When the MOSFETs inside a processor switches, it consumes currents during transition time. If this current is not provided, the voltage on the supply rails can go below the specifications of the processor. For lower MHz processors few ceramic-capacitors known as ‘decoupling capacitors’ were connected between power and ground to provide this transient current demand. When the processor frequency increased beyond MHz, the number of capacitors also increased from few numbers to hundreds of them. Nowadays, the PDN is said to be comprising all components from VRM till the die location. It includes VRM, bulk capacitors, PCB power planes, capacitor mounting pads and vias, mount for the electronic package, package capacitors, die mount and internal die capacitance. So, the PDN has evolved into a very complex system over the years. A PDN should provide three distinct roles; 1) provide transient current required by the processor 2) act as a stable reference voltage for processor 3) filter out the noise currents injected by the processor. The first two are required for the correct operation of the processor. Third one is a requirement from analog or other sensitive circuits connected to the same PDN. If the noise exits the printed circuit board (PCB), it can result in conducted and radiated EMI, which can in turn result in failure of a product in EMC testing. Every PDN design starts with the calculation of a target impedance which is given as the ratio of maximum allowed ripple voltage to the maximum transient current required by the processor. The transient current is usually taken as half the average input current. The definition of target impedance assumes that the PDN is flat over the entire frequency of operation, which is true only for a resistive network. This is seldom true for a practical PDN, since it contains inductances and capacitances. Because of this, a practical PDN has an uneven impedance versus frequency envelope. Whenever two capacitors with different self resonant frequencies are connected in parallel, their equivalent impedance produces a pole between the self resonant frequencies known as antiresonance peaks. Because of this, a PDN will have phase angles associated with them. Also, these antiresonance peaks are energy reservoirs which will be excited during the normal operation of a processor by the varying currents. The transient current of a microprocessor is modeled as a gamma function, but for practical cases it can be approximated as triangular waveforms during the transition time which is normally 10% of the time period. Depending upon the micro-operations running inside the processor, the peak value of this waveform varies. This is filtered by the on-chip capacitors, package inductance and package capacitors. Due to power gating, clock gating, IO operations, matrix multiplications and magnetic memory readings the waveforms at the board will be like pulse type, and their widths are determined by these operations. In literatures, these two types of waveforms are used for PDN analysis, depending upon at which point the study is conducted. Chapter 1 introduces the need for PDN design and the main roles of a PDN. The issue of antiresonance is introduced from a PDN perspective. Different types of capacitors used on a PDN are discussed with their strengths and limitations. The general nature of the switching noise injected by a microprocessor is also discussed. This chapter discusses the thesis contributions, and the existing work related to the field. Chapter 2 introduces a new method to calculate the target impedance (Zt ) by including the phase angles of a PDN which is based on a maximum voltage calculation. This new Zt equals to conventional Zt for symmetrical triangular switching current waveforms. The value of new Zt is less than the conventional Zt for trapezoidal excitation patterns. By adding the resonance effects into this, a maximum voltage value is obtained in this chapter. The new method includes the maximum voltage produced on a PDN when multiple antiresonance peaks are present. Example simulations are provided for triangular and pulse type excitations. A measured input current wave-form for PIC16F677 microcontroller driving eight IO ports is provided to prove the assumption of pulse type waveforms. For triangular excitation waveform, the maximum voltage predicted based on the expression was ¡0.6153 V, and the simulated maximum voltage was found to be at ¡0.5412 V which is less than the predicted value. But the predicted value based on Zt method was 1.9845 V. This shows that the conventional as well as the new target impedance method leads to over estimating the maximum voltage in certain cases. This is because most of the harmonics are falling on the minimum impedance values on a PDN. If the PDN envelope is changed by temperature and component tolerances, the maximum voltage can vary. So the best option is to design with the target impedance method. When pulse current excitation was studied for a particular PDN, the maximum voltage produced was -139.39 mV. The target impedance method produced a value of -100.24 mV. The maximum voltage predicted by the equation was -237 mV. So this shows that some times the conventional target impedance method leads to under estimating the PDN voltage. From the studies, it is shown that the time domain analysis is as important as frequency domain analysis. Another important observation is that the antiresonance peaks on a PDN should be damped both in number and peak value. Chapter 3 studies the antiresonance peak suppression methods for general cases. As discussed earlier, the antiresonance peaks are produced when two capacitors with different self resonant frequencies are connected in parallel. This chapter studies the effect of magnetic coupling between the mounting loops of two capacitors in parallel. The mounting loop area contribute to the parasitic inductance of a capacitor, and it is the major contributing factor to it. Other contributing factors are equivalent series inductance (ESL) and plane spreading inductance. The ESL depends on the size and on how the internal plates of the capacitors are formed. The spreading inductance is the inductance contributed by the parts of the planes connecting the capacitor connector vias to the die connections or to other capacitor vias. If the power and ground planes are closer, the spreading inductance is lower. On one/two layer boards dedicated power/ground planes are absent. So the spreading inductance is replaced by PCB track inductances. The inductance contributed by the mounted area of the capacitor is known as mounting inductance. On one/two layer boards dedicated power/ground planes are absent. So the spreading inductance is replaced by PCB track inductances. The dependencies of various circuit parameters on antiresonance peak are studied using circuit theory. A general condition for damping the antiresonance is formulated. The antiresonance peak reduces with Q factor. The conventional critical condition for antiresonance peak damping needs modification when magnetic coupling is present between the mounting loops of two parallel unequal value capacitors. By varying the connection geometry it is possible to obtain negative and positive coupling coefficients. The connection geometries to obtain these two are shown. An example is shown for positive and negative coupling coefficient cases with simulation and experimental results. For the example discussed, RC Æ 32 - for k Æ Å0.6 and RC Æ 64 - for k Æ ¡0.6, where RC is the critical damping value and k is the magnetic coupling coefficient between the two mounting loops. The reason for this is that, the antiresonance peak impedance value is higher for negative coupling coefficient case than that for positive coupling coefficient case. Above the self resonant frequencies of both the capacitors, the equivalent impedance of the parallel capacitors become inductive. This case is studied with two equal value capacitors in parallel. It is shown that the equivalent inductance is lower for negative coupling coefficient case as compared to positive coupling coefficient case. An example is provided with simulation and experimental results. In the experimental results, parasitic inductance is observed to be 2.6 times lower for negative coupling coefficient case than that for positive coupling coefficient case. When equal value capacitors are connected in parallel, it is advantageous to use a negative coupling geometry due to this. Chapter 4 introduces a new method to damp the antiresonance peak using a magnet-ically coupled resistive loop. Reducing the Q factor is an option to suppress the peak. In this new method, the Q factor reduction is achieved by introducing losses by mag-netically coupling a resistive loop. The proposed circuit is analyzed with circuit-theory, and governing equations are obtained. The optimum value of resistance for achieving maximum damping is obtained through analysis. Simulation and experimental results are shown to validate the theory. From the experimental results approximately 247 times reduction in antiresonance peak is observed with the proposed method. Effectiveness of the new method is limited by the magnetic coupling coefficient between the two mounting loops of capacitors. The method can be further improved if the coupling coefficient can be increased at the antiresonance frequency. Chapter 5 focuses on the third objective of a PDN, that is to reduce the noise injected by the microprocessor. A new method is proposed to reduce the conducted noise from a microprocessor with switched super capacitors. The conventional switched capacitor filters are based on the concept that the flying capacitor switching at high frequency looks like a resistor at low frequency. So for using at audio frequencies the flying capacitors were switching at MHz frequencies. In this chapter the opposite of this scenario is studied; the flying capacitors are the energy storage elements of a switched capacitor converter and they switch at lower frequencies as compared to the noise frequencies. Two basic circuits (1:1 voltage conversion ratio) providing noise isolation were discussed. They have distinct steady state input current waveforms and are explained with PSPICE simulations. The inrush current through switches are capable of destroying them in a practical implementation. A practical solution was proposed using PMOS-PNP pair. The self introduced switching noise of the converter is lower when switching frequency is low and turn ON-OFF time is higher. If power metal oxide semiconductor field effect transistor (MOSFET)s are used, the turn ON and turn OFF are slow. The switching frequency can be lowered based on the voltage drop power loss. The governing equations were formulated and simulated. It is found that the switching frequency can be lowered by increasing the capacitance value without affecting the voltage drop and power loss. From the equations, it is found that the design parameters have a cyclic dependency. Noise can short through the parasitic capacitance of the switches. Two circuits were proposed to improve the noise isolation: 1) T switch 2) ¦ switch. Of these, the ¦ switch has the higher measured transfer impedance. Experimental results showed a noise reduction of (40-20) dB for the conducted frequency range of 150 kHz - 30 MHz with the proposed 1:1 switched capacitor converter. One possible improvement of this method is to combine the noise isolation with an existing switched capacitor converter (SCC) topology. The discussed example had a switching frequency of 700 Hz, and it is shown that this can isolate the switching noise in kHz and MHz regions. In a PDN there are antiresonance peaks in kHz regions. If the proposed circuit is kept close to a microprocessor, it can reduce the excitation currents of these low frequency antiresonance peaks. Chapter 6 concludes the thesis by stating the major contributions and applications of the concepts introduced in the thesis. This chapter also discusses the future scope of these concepts.

Made available in DSpace on 2016-08-17T14:53:20Z (GMT). No. of bitstreams: 1 Tiago Brito Bezerra.pdf: 3848907 bytes, checksum: 09c5f40ad1ac5ce43a253e0335d491da (MD5) Previous issue date: 2012-04-13 / Coordenação de Aperfeiçoamento de Pessoal de Nível Superior / Programmable integrated circuits enable its adjustment after fabrication to fit more than one application within a certain set of applications. A programmable measurement system can be applied to the measurement of different quantities involving a set of sensors with different signal characteristics and employing a single analog-to-digital converter (ADC). The output signal range for each sensor should be adjusted to be as close to the input range of the ADC as possible, to ensure maximum measurement quality. One solution to implement the adjustment on the signal range is the use of a measurement system with programmable conditioning circuit. In this work, it is proposed to design an ADC integrated circuit whose input range is adjusted to the signal level at the output of the sensor in order to avoid amplification stages in a signal conditioning circuit. For this adjustment, the input of the converter should be programmable, making it more compatible with various sensors with different characteristics. The developed ADC also allows the configuration of the converter resolution, enabling the designer to exploit trade-offs between resolution and conversion speed for a given application. The ADC is a switched capacitor integrating converter and it was designed for the AMS 0.35 μm CMOS process. / Circuitos integrados programáveis possibilitam o seu ajuste após a fabricação, para se adequarem a mais de uma aplicação dentro de um conjunto determinado de aplicações. Um sistema de medição programável pode ser aplicado em medições que envolvam um conjunto de sensores com características diferentes de sinais e um conversor analógico-digital. A faixa de sinal em cada sensor deve ser ajustada o mais próximo da faixa de entrada do conversor analógico-digital, para garantir a medição com a faixa completa do sinal. Uma solução para realizar o ajuste da faixa do sinal é o uso de um sistema de medição com circuito de condicionamento programável. Neste trabalho de dissertação, propõe-se o projeto de um conversor analógico-digital em circuito integrado em que a faixa de entrada pode ser ajustada ao nível de sinal na saída do sensor, com a finalidade de evitar estágios de amplificação do sinal em um circuito de condicionamento. Para tal ajuste, a entrada do conversor deverá ser programável, o que o torna mais compatível com diversos sensores com características diferentes. O circuito proposto também possibilita a definição da resolução do conversor o que permite a escolha de compromisso entre resolução e velocidade de conversão, dependendo da aplicação. O conversor A/D é do tipo integrador a capacitores chaveados e foi projetado, em nível de transistor e leiaute, para o processo AMS 0,35 m CMOS.

Les récentes avancées technologiques des microphones de type microsystème électromécanique (MEMS) leurs permettent une utilisation sur une large gamme d’amplitudes sonores. Leur niveau de bruit ayant baissé, il devient possible de capter des sons provenant d’une distance plus lointaine, tandis que l’augmentation de leur pression acoustique maximale leur permet de ne pas saturer dans un environnement très bruyant de type concert ou évènement sportif. Ainsi le système électronique de conversion analogique-numérique connecté au microphone devient l’élément limitant les performances du système d’acquisition acoustique. Un besoin de nouvelles architectures de conversion analogique-numérique ayant une plage dynamique augmentée se fait donc ressentir. Par ailleurs, ces microphones étant de plus en plus utilisés dans des systèmes fonctionnant sur batterie, la contrainte de limitation de la consommation devient importante.Dans la bande de fréquences audio, les convertisseurs analogiques-numériques de type sigma-delta sont les plus aptes à obtenir une grande résolution combinée à une faible consommation. Ils sont divisés en deux grandes familles: ceux à temps discret utilisant principalement des circuits à capacités commutées, et ceux à temps continu utilisant des circuits classiques. Cette thèse se concentre sur l’étude et la conception de chacun des deux types de convertisseurs sigma delta, en insistant sur la faible consommation, le faible coût de production (surface occupée) et la robustesse du circuit, cela en vue d’une production de masse pour équipements portables.La conception d’un convertisseur analogique numérique de type sigma-delta à temps discret a été réalisé, ce dernier atteignant un rapport signal sur bruit de 100 décibels sur une bande de 24kHz, pour une puissance consommée de seulement 480μW. Pour limiter la consommation, de nouveaux amplificateurs à base d’inverseurs sont utilisés, et dont la robustesse contre les variations du procédé de fabrication ou de la température a été améliorée. Les spécifications ont été définies grâce au développement d’un modèle de haut-niveau précis, ce qui permet d’éviter le surdimensionnement tout en atteignant les performances voulues. Enfin, un grand ratio de suréchantillonnage a été choisi afin de réduire l’espace utilisé par les capacités commutées, minimisant le coût de fabrication.Après une étude théorique de l’équivalence entre les modulateurs sigma-delta à temps discret et à temps continu, ainsi que des spécificités propres aux modulateurs à temps continu, une réalisation de ces derniers a été effectuée. Celui-ci atteint un rapport signal sur bruit de 95 décibels sur une bande de fréquence de 24kHz, tout en consommant 142μW. Pour réduire la consommation ainsi que l’espace utilisé, un filtre de boucle du second-ordre a été réalisé avec un seul amplificateur, et le quantificateur fait aussi office d’intégrateur grâce à l’utilisation d’une structure d’oscillateurs contrôlés en tension. Ce quantificateur à base d’oscillateurs est réalisé par des cellules numériques, réduisant la consommation et l’espace utilisé, mais est hautement non-linéaire. Cette non-linéarité a été prise en compte par des choix architecturaux afin de ne pas réduire les performances finales du modulateur. / The recent technological advances in microelectromechanical system (MEMS) microphones allow them to be used on a large sound amplitude range. Due to their lower noise level, it becomes possible to capture sound from a faraway distance, while their increased acoustic overload point gives them the ability to capture sound without saturation in a loud environment like a concert or a sport event. Thus, the electronic analog / digital conversion system connected to the microphone becomes the limiting element of the acoustic acquisition system performance. There is then a need for a new analog / digital conversion architecture which has an increased dynamic range. Furthermore, since more and more of these microphones are used in battery-powered devices, the power consumption limitation constraint becomes of high importance.In the audio frequency band, the sigma-delta analog / digital converters are the ones most able to provide a high dynamic range combined to a limited power consumption. They are split in two families: the discrete-time ones using switched-capacitors circuits and the continuous-time ones using more classical structures. This thesis concentrates on the study and the design of both of these two types of sigma-delta converters, with an emphasis on the low-power consumption, the low production cost (area occupied) and the circuit robustness, in sight of a mass production for portable devices.A discrete-time sigma-delta modulator design has been made, the latter reaching a signal to noise ratio of 100dB on a 24kHz frequency bandwidth, for a power consumption of only 480μW. To limit the power consumption, new inverter-based amplifiers are used, with an improved robustness against the variations of the fabrication process or the temperature. Amplifier specifications are obtained thanks to an accurate high-level model developed, which allows to avoid over-design while ensuring that the wanted performances are reached. Finally, a large oversampling ratio has been used to reduce the switched-capacitors area, lowering the modulator cost.After a theoretical study of the equivalence between discrete-time and continuous-time modulators, and of continuous-time modulators specificities, a design of the latter has been made too. It reaches a signal to noise ratio of 95dB on a 24kHz bandwidth, while consuming 142μW. To reduce the power consumption and the occupied area, a second-order loop filter is implemented using a single amplifier, and the quantizer uses a VCO-based structure that provides inherently an integrating stage. The VCO-based quantizer is made using digital cells, lowering the consumption and area, but is highly non-linear. This non-linearity has been handled by architectural choices to not influence the final modulator performances.

Made available in DSpace on 2016-08-17T14:53:14Z (GMT). No. of bitstreams: 1 Rafael Oliveira Nunes.pdf: 2514852 bytes, checksum: 72d45d30f5d3d54f97f6401ca5005607 (MD5) Previous issue date: 2010-12-23 / Coordenação de Aperfeiçoamento de Pessoal de Nível Superior / Programmable integrated circuits for specified applications enable its adjustment after fabrication, to fit more than one application within a certain set of applications. These circuits are flexible, but could lose in performance when compared to other circuit constructed to serve only a specific application. A programmable system can be applied to measurements involving a set of sensors with different characteristics of signals and an analog-to-digital converter. The signal range for each sensor should be adjusted as close to the input range of analog-digital converter as possible, to ensure the measurement with the full range of the signal. A solution for ensure the adjustable ranges is the employ a measurement system with programmable conditioning circuit. In this work, an analog-to-digital converter with adjustable input range is proposed, providing, equivalently, an adjustable gain value to the analog input signal. The gain values compose a minimum set to ensure no loss of measurement range of the signal, with loss of resolution within an acceptable limit. The proposed converter is a discrete integrator type with switched capacitor circuits. Behavioral and SPICE simulations were performed to validate the proposed converter. / Circuitos integrados programáveis possibilitam o seu ajuste após a fabricação, para se adequar a mais de uma aplicação dentro de um conjunto determinado de aplicações. Esses circuitos são flexíveis, mas podem perder em desempenho quando comparado a outro circuito fabricado para servir a apenas uma aplicação específica. Um sistema programável pode ser aplicado em medições que envolvam um conjunto de sensores com características diferentes de sinais e um conversor analógico-digital. A faixa de sinal em cada sensor deve ser ajustada o mais próximo da faixa de entrada do conversor analógico-digital, para garantir a medição com a faixa completa do sinal. Uma solução para garantir o ajuste das faixas é o uso de um sistema de medição com circuito de condicionamento programável. Neste trabalho, um conversor analógico-digital com faixa de entrada ajustável é proposto, proporcionando, de forma equivalente, um valor de ganho ajustável ao sinal analógico de entrada. Os valores de ajuste pertencem a um conjunto mínimo de ganhos definidos para garantir que não haja perda da faixa de medição do sinal, com perda de resolução dentro de um limite aceitável. O conversor proposto é do tipo integrador discreto com circuitos a capacitor chaveado. Simulações comportamentais e em SPICE foram realizadas de forma a validar o conversor proposto.

This Master`s thesis is focused on through acquaintance of principles of the function circuits with switched capaticors and posibility of their application mainly in frequency filters or signal generators. The origin of the switched capacitor circuits is mentioned at the beginning of the work. There are references to the first scientific work and scientists who have dealt with this issue. Maxwell`s idea: lossy element (resistor) replace with lossless element (switched capacitor) in electric circuit, is further described. In the next chapter of this work are listed types of switching capacitors and their use in simple RC filters and in structures of inverted or noninverted integrators and their application in more complex higher order filters. The advantages and disadvantages of SC circuits versus circuit composed of discrete components are shown. It is also listed a simple low-pass switched RC filter implemented with analogue multiplexer 4053. Using the LTC1043 integrated circuit, which structure and properties are described and analyzed in detail in the work, the 1st order aktive or pasive low and high pass filters were designed and subsequently simulated in the computer simulator OrCAD PSpice v.10. Another chapter deals with the integrated circuits higher order filters, structure and properties of the integrated filter LTC1060 are further analyzed here. Except this IC there are mentioned integrated filters commercially less available from the corporations Linear Technology and Maxim. The main objective of thesis was to propose and establish laboratory device and laboratory measurment focused on the switched capacitor circuits. The laboratory device has been designed with integrated circuits LTC1043 and LTC1060, which is demonstrated by using passive and active integrator, 2nd order band-pass and 4th order band-pass with Chebyshevovou approximation.

Ultra low power wireless sensors and sensor systems are of increasing interest in a variety of applications ranging from structural health monitoring to industrial process control. Electrochemical batteries have thus far remained the primary energy sources for such systems despite the finite associated lifetimes imposed due to limitations associated with energy density. However, certain applications (such as implantable biomedical electronic devices and tire pressure sensors) require the operation of sensors and sensor systems over significant periods of time, where battery usage may be impractical and add cost due to the requirement for periodic re-charging and/or replacement. In order to address this challenge and extend the operational lifetime of wireless sensors, there has been an emerging research interest on harvesting ambient vibration energy. Vibration energy harvesting is a technology that generates electrical energy from ambient kinetic energy. Despite numerous research publications in this field over the past decade, low power density and variable ambient conditions remain as the key limitations of vibration energy harvesting. In terms of the piezoelectric transducers, the open-circuit voltage is usually low, which limits its power while extracted by a full-bridge rectifier. In terms of the interface circuits, most reported circuits are limited by the power efficiency, suitability to real-world vibration conditions and system volume due to large off-chip components required. The research reported in this thesis is focused on increasing power output of piezoelectric transducers and power extraction efficiency of interface circuits. There are five main chapters describing two new design topologies of piezoelectric transducers and three novel active interface circuits implemented with CMOS technology. In order to improve the power output of a piezoelectric transducer, a series connection configuration scheme is proposed, which splits the electrode of a harvester into multiple equal regions connected in series to inherently increase the open-circuit voltage generated by the harvester. This topology passively increases the rectified power while using a full-bridge rectifier. While most of piezoelectric transducers are designed with piezoelectric layers fully covered by electrodes, this thesis proposes a new electrode design topology, which maximizes the raw AC output power of a piezoelectric harvester by finding an optimal electrode coverage. In order to extract power from a piezoelectric harvester, three active interface circuits are proposed in this thesis. The first one improves the conventional SSHI (synchronized switch harvesting on inductor) by employing a startup circuitry to enable the system to start operating under much lower vibration excitation levels. The second one dynamically configures the connection of the two regions of a piezoelectric transducer to increase the operational range and output power under a variety of excitation levels. The third one is a novel SSH architecture which employs capacitors instead of inductors to perform synchronous voltage flip. This new architecture is named as SSHC (synchronized switch harvesting on capacitors) to distinguish from SSHI rectifiers and indicate its inductorless architecture.